Circuit and method for frequency synthesis for signal detection in automatic voltage regulation for synchronous generators

ABSTRACT

Automatic voltage regulation is shown involving full wave rectifying a power signal and generating a reference corresponding to an operating voltage level, line sampling the power signal and comparing it to the reference to generate a line sync signal synchronized to the power signal. Producing 90° out of phase signals synchronized to the line sync signal with a PLL locked onto the line sync signal that outputs a phase error signal. Generating a quadrature signal from the phase signals. Sampling the peaks of the rectified power signal using the quadrature signal to produce a control signal. Subtracting the error signal and damping signal from the reference to produce a duty cycle modulation signal. The duty cycle modulation signal controls a duty cycle of a field voltage control signal that oscillates at a predetermined frequency. The field voltage control signal is low-pass filtered to produce the damping signal.

BACKGROUND

The present invention relates to automatic voltage regulation and, moreparticularly, to voltage control for synchronous generators.

Synchronous generators are generally used to produce alternating current(AC) power, such as the 120 volts AC (VAC) at a frequency of 60 Hertz(Hz) that is the standard in much of North America. Synchronousgenerators typically feature precise control of voltage, frequency, andpower, which is achieved through the use of voltage regulators. FIG. 1is a simplified circuit diagram illustrating an example of a synchronousgenerator 10. Synchronous generator 10 is composed of a stationaryarmature winding, stator 12, with multiple wired connected in series orparallel to obtain a desired voltage for the output voltage VGEN of thegenerator. The armature winding is typically placed into a slottedlaminated steel core. The generator also includes a rotor having rotorwinding 14, which is fed with a DC field current to produce anelectromagnetic field that rotates with the rotor to produce a revolvingfield with a strength that is proportional to the field current.

A mutual flux develops across an air gap between the rotor and stator,which interact to produce an electro-magnetic force (EMF). As magneticflux developed by the DC field poles of the rotor winding 14 crosses theair gap of the stator windings 12, a sinusoidal voltage is produced andoutput by the generator as VGEN. The magnitude of the AC voltage VGENoutput by the generator is controlled by the amount of DC excitationcurrent that is supplied to the field winding 14 of the rotor. Thefrequency of the voltage developed by generator 10 depends upon thespeed of the rotor, which is also affected by the excitation currentsupplied to the rotor field winding 14. The frequency of the generatorwill typically be influenced by variations or transients of the load onthe generator. For example, a sudden increase in the load may cause areduction of the generator's frequency.

An Automatic Voltage Regulator (AVR) 16 is a device that controls theoutput voltage of a synchronous electric generator to keep the outputvoltage constant as load changes. This is achieved by controlling theField Current IFIELD in the field winding 14 of the rotor as a functionof the generator's output voltage. AVR 16 controls IFIELD by controllingthe field voltage VFIELD output to power section 18, which is generallya relatively high current device. The field winding 14 of the rotor canbe connected directly to the AVR 16 and power section 18 by slipringsand brushes, but another approach is brushless excitation, wherein thefield winding 14 is fed by an exciter thus eliminating the brushes.

AVRs are typically used to control the field or excitation current tothe rotor in order to maintain the output voltage of the generator at aconstant frequency and voltage. A typical automatic voltage regulator(AVR) monitors the output voltage VGEN of the generator and modulatesthe excitation current IFIELD to rotor field winding 14 in response tovariations in frequency and voltage level of VGEN, which will beaffected by variations in load 20 coupled to the generator output.

The aim of AVR design is to maximize performance for a given PrimeMover/Exciter/generator configuration. One of ordinary skill in the artwould generally understand this to mean (1) control the output voltagewithin a small deviation range (e.g. less than 3%) of the nominalvoltage on a steady state condition and (2) respond rapidly to changingloads, i.e the transient response is designed in a way that protects theload connected to it and makes good use of the prime/mover/generatorbeing controlled. Often the AVR will be required to start up fromresidual magnetism (i.e. there is no separate power supply from whichthe AVR can excite the rotor winding in order to start the generatorfunction).

There are generally four main performance considerations that arenormally addressed in AVR design in order to control the generatoroutput voltage under varying load conditions. A first designconsideration is to adjust the generator output voltage within a givenrange (usually +/−10% around a nominal voltage, i.e. 120 VAC line toground) and maintain the selected voltage in spite of load changes. Insteady state conditions, most modern AVRs will maintain the voltagewithin 3% regulation or better from no load to full load. Some modernAVRs can maintain 1% regulation, but, in practice, anything below about2% provides no significant benefit since electric utilities voltageregulation can often change as much as 5% and most loads are rated tooperate properly within a range of +/−10% of the nominal line voltagelevel.

A second AVR design consideration is regulating under heavy transientloads to minimize the initial voltage drop. FIG. 2 is a graphillustrating a typical transient response of a conventional AVR inresponse to the introduction of a heavy transient load, such as theactivation of a motor. An AVR is generally expected to minimize theinitial voltage drop and then recover to steady state regulation within3% or better of specified voltage output from no load to full load. Asub-transient voltage drop period immediately following the introductionof the heavy transient typically averages five cycles, which is shown inthe graph of FIG. 2 at an 80 millisecond period at 87 V. Thesub-transient period is followed by a transient period wherein thevoltage output recovers to within a given tolerance of the target outputvoltage level. The sum of the two periods is usually termed recoverytime. In many AVRs, the sub-transient voltage drop is in the range of25-30% for a recovery time in the range of 250 to 500 milliseconds for atransient load demand ranging from 5% to 95% of the generator's ratedcapacity in kilo-volt-amperes (KVA).

A third common AVR design consideration is to maintain a constant Voltto Hertz (V/Hz) ratio in spite of frequency variations, thus avoidingsaturation of the electromagnetic components of the load (e.g.transformers, motors, etc.). This characteristic should have anadjustable start frequency (i.e. the maximum frequency from which theV/Hz ratio starts, such as 60 Hz) and vary from the maximum operatingfrequency to a minimum that is the lowest expected frequency expectedduring an overload.

A fourth AVR design consideration is to provide a flexible V/Hzcapability that can be adjusted so as to assist the recovery of theprime mover/exciter/generator combinations in case of a heavy transientoverload. Flexibility means, in this case, to have the ability to: (A)adjust the V/Hz ratio from 1:1 to a higher value so that the outputvoltage will drop faster as the prime mover speed decreases as a resultof a transient overload; and (B) set the frequency at which the V/Hzratio begins to automatically adjust, such as a predetermined frequencybelow 60 Hz (usually between 59.5 Hz to 57 Hz) in order to provideregulation for light to moderate load changes.

The above four considerations are typically sufficient for stand-alonegenerator operation. If parallel operation is called for, then a fifthconsideration called droop control may be required, which may be readilycombined with some embodiments of the present invention.

SUMMARY

According to one aspect of the present invention, an automatic voltageregulator circuit is shown that has a direct current power supplycircuit that receives a power signal to be regulated, full waverectifies the received power signal and generates a DC reference voltagesignal, where the DC reference voltage corresponds to a desired steadystate operating voltage level for the power signal. A line samplingcircuit receives the power signal and compares it to the DC referencevoltage signal in order to generate a line sync signal synchronized tothe oscillation of the power signal. A quadrature signal generatorcircuit receives the line sync signal and produces a pair of phasesignals that are synchronized to the line sync signal and 90° out ofphase with one another. The quadrature signal generator circuit includesa phase locked loop circuit configured to lock onto the frequency of theline sync signal using a lock frequency that is at least twice theoscillation frequency of the power signal, where the phase locked loopcircuit outputs a phase error signal that corresponds to a phasedifference between the line sync signal and an oscillating frequency ofthe phase locked loop. A quadrature sync circuit receives the two phasesignals and generates a quadrature signal that is in quadrature with theline sync signal. A sample and hold circuit receives the quadraturesignal and the full wave rectified power signal and samples the peakvoltages of the full wave rectified power signal using the quadraturesignal and holds the sampled peak voltages to produce a voltage levelcontrol signal representing a current absolute magnitude of theamplitude of the power signal. An error amplifier receives the referencevoltage, the voltage level control signal, and a damping signal andsubtracts the error signal and the damping signal from the referencevoltage in order to produce a duty cycle modulation signal. A duty cyclemodulator circuit receives the duty cycle modulation signal and producesa field voltage control signal that oscillates at a predeterminedfrequency with a duty cycle controlled by the duty cycle modulationsignal. A stabilizer circuit low-pass filters the field voltage controlsignal to produce the damping signal. In a preferred refinement, thephase locked loop of the quadrature signal generator circuit operates ata lock frequency that is at least four times the oscillation frequencyof the power signal.

A refinement of the automatic voltage regulator circuit includes afrequency control circuit that receives a frequency reference voltageand the phase error signal and subtracts the frequency reference voltagefrom the phase error signal to produce a frequency control signalrepresenting a phase correction for the power signal. The erroramplifier circuit is modified to receive the frequency control signaland subtract it from the reference voltage in producing the duty cyclemodulation signal. In another refinement, the error amplifier circuit isconfigured to receive a droop control signal and subtract it from thereference voltage in producing the duty cycle modulation signal.

One refinement of the automatic voltage regulator circuit includes adigital frequency control circuit converts the phase error signal to adigital phase error signal, multiplies the digital phase error signal bya voltage to Hertz slope parameter, subtracts a reference voltageparameter, and multiplies by a scaling factor to produce a scaledfrequency error signal. The digital frequency control circuit alsocompares the scaled frequency error signal to a frequency thresholdparameter and, if the scaled frequency error signal value is less thanthe frequency threshold parameter, sets a frequency control value to areference value corresponding to a desired frequency of the powersignal, and, otherwise, sets the frequency control value to thefrequency threshold parameter. Further, the digital frequency controlcircuit multiplies the frequency control value by an output voltagelevel parameter to produce a digital frequency control signal andconverts the digital frequency control signal to an analog frequencycontrol signal. In this refinement, the error amplifier circuit ismodified to subtract the analog frequency control signal from thereference voltage in producing the duty cycle modulation signal.

In still another refinement of the automatic voltage regulator circuit,the error amplifier is composed of a digital error amplifier circuitthat converts the voltage level control signal to a digital voltagelevel control signal, low pass filters the field voltage control signalto produce a damping signal, and converts the damping signal to adigital damping signal. The digital error amplifier circuit multipliesthe digital damping signal by a predetermined damping factor to producea modified digital damping signal, computes a difference between themodified digital damping signal and the digital voltage level controlsignal to produce a digital difference signal, and multiplies thedigital difference signal by a predetermined gain factor to produce anamplified digital difference signal. The digital error amplifier pulsewidth modulation encodes the amplified digital difference signal toproduce the duty cycle modulation signal.

According to another aspect of the present invention, a method is shownfor automatic voltage regulation of a generator involving full waverectifying a power signal of the generator, sampling the power signaland comparing it to a DC reference voltage signal corresponding to adesired steady state operating voltage level for the power signal inorder to generate a line sync signal synchronized to an oscillationfrequency of the power signal. The method also calls for producing firstand second phase signals that are synchronized to the line sync signaland 90° out of phase with one another. The method further involves usinga phase locked loop to lock onto the frequency of the line sync signalusing a lock frequency that is at least twice the oscillation frequencyof the power signal and generating a phase error signal that correspondsto a phase difference between the line sync signal and an oscillatingfrequency of the phase locked loop. Using the first and second phasesignals, a quadrature signal is generated that is in quadrature with theline sync signal. The method also includes sampling the peak voltages ofthe full wave rectified power signal using the quadrature signal andholding the sampled peak voltages to produce a voltage level controlsignal representing a current absolute magnitude of the amplitude of thepower signal. The error signal and the damping signal are subtractedfrom the reference voltage in order to produce a duty cycle modulationsignal. The duty cycle modulation signal is used to produce a fieldvoltage control signal, where the field voltage control signaloscillates at a predetermined frequency with a duty cycle controlled bythe duty cycle modulation signal. The damping signal is produced bylow-pass filtering the field voltage control signal. In a preferredrefinement, the lock frequency of the phase locked loop is at least fourtimes the oscillation frequency of the power signal.

A further refinement of the method calls for subtracting a frequencyreference voltage from the phase error signal to produce a frequencycontrol signal representing a phase correction for the power signal andproducing the duty cycle modulation signal further involves subtractingthe frequency control signal from the reference voltage.

Another refinement of the method calls for converting the phase errorsignal to a digital phase error signal, multiplying the digital phaseerror signal by a voltage to Hertz slope parameter, subtracting areference voltage parameter, and multiplying by a scaling factor toproduce a scaled frequency error signal. The scaled frequency errorsignal is compared to a frequency threshold parameter and, if the scaledfrequency error signal value is less than the frequency thresholdparameter, a frequency control value is set to a reference valuecorresponding to a desired frequency of the power signal, and,otherwise, the frequency control value is set to the frequency thresholdparameter. A digital frequency control signal is produced by multiplyingthe frequency control value by an output voltage level parameter. Thedigital frequency control signal is converted to an analog frequencycontrol signal. And producing the duty cycle modulation signal furtherinvolves subtracting the analog frequency control signal from thereference voltage.

Still another refinement of the method calls for converting the voltagelevel control signal to a digital voltage level control signal, low passfiltering the field voltage control signal to produce a damping signal,and converting the damping signal to a digital damping signal. Amodified digital damping signal is produced by multiplying the digitaldamping signal by a predetermined damping factor. A difference iscomputed between the modified digital damping signal and the digitalvoltage level control signal to produce a digital difference signal. Thedigital difference signal is multiplied by a predetermined gain factorto produce an amplified digital difference signal. And the amplifieddigital difference signal is pulse width modulation encoded to producethe duty cycle modulation signal.

BRIEF DESCRIPTION OF THE DRAWINGS

Various embodiments in accordance with the present disclosure will bedescribed with reference to the drawings, in which:

FIG. 1 is a schematic diagram illustrating a simplified example of agenerator system with automatic voltage regulation;

FIG. 2 is a graph illustrating an example of a transient response of aconventional automatic voltage regulator;

FIG. 3 is a functional block diagram illustrating an example of anautomatic voltage regulator system in accordance with the presentinvention;

FIG. 4 is a diagram illustrating a comparison of one example of a linesampling signal to a sampled generator output voltage signal;

FIG. 5 is a functional block diagram illustrating an example of atransfer function for automatic voltage regulation in accordance withthe present invention;

FIG. 6 is a waveform diagram illustrating an example of sampling of arectified power signal to obtain a representation of a voltage level ofthe generator output voltage;

FIG. 7 is a functional block diagram illustrating another example of anautomatic voltage regulator in accordance with some aspects of thepresent invention;

FIG. 8 is a circuit diagram illustrating an example of one embodiment ofcircuitry for the DC power supply and line sampling circuits shown inFIG. 7;

FIG. 9 is a circuit diagram illustrating an example of one embodiment ofcircuitry for the quadrature signal generator with phase locked loopcircuit shown in FIG. 7;

FIG. 10 is a circuit diagram illustrating an example of one embodimentof circuitry for the quadrature synchronization circuit shown in FIG. 7;

FIG. 11 is a circuit diagram illustrating an example of one embodimentof circuitry for the power section circuit shown in FIG. 7;

FIG. 12 is a circuit diagram illustrating an example of one embodimentof circuitry for the error amplifier circuit shown in FIG. 7;

FIG. 13 is a circuit diagram illustrating an example of one embodimentof circuitry for the sample and hold circuit shown in FIG. 7;

FIG. 14 is a circuit diagram illustrating an example of one embodimentof circuitry for the duty cycle modulator circuit shown in FIG. 7;

FIG. 15 is a circuit diagram illustrating an example of one embodimentof circuitry for the voltage to hertz control circuit shown in FIG. 7;

FIG. 16 is a photograph of an oscillogram illustrating a relationshipbetween a line voltage sample signal and an output signal from a phaselocked loop circuit in one example of an automatic voltage regulator;

FIG. 17 is a photograph of an oscillogram illustrating a relationshipbetween a line voltage sample signal and a quadrature signal produced inone example of an automatic voltage regulator;

FIG. 18 is a photograph of an oscillogram illustrating a relationshipbetween a line voltage signal and sampling pulses produced in oneexample of an automatic voltage regulator;

FIG. 19 is a photograph of an oscillogram comparing an example of anautomatic voltage control signal sample produced by a conventionalcircuit using rectification and filtering and a control signal producedin one example of the present automatic voltage regulator;

FIG. 20 is a photograph of an oscillogram illustrating a relationshipbetween an error signal and a corresponding output signal from a choppercircuit in response to a transient load event in one example of anautomatic voltage regulator;

FIG. 21 is a photograph of an oscillogram illustrating a relationshipbetween the error signal of FIG. 20 and an output voltage of a generatorin response to the transient load event of FIG. 20 in one example of anautomatic voltage regulator;

FIG. 22 is a control flow diagram illustrating the steps or stages of anexemplary process for voltage to hertz control that may be performed ina processor or similar device to implement a digital embodiment ofanother example of an automatic voltage regulator;

FIG. 23 is a control flow diagram illustrating the steps or stages of anexemplary process for that may be performed in a processor or similardevice to digitally produce an error signal in a digital embodiment ofanother example of an automatic voltage regulator; and

FIG. 24 is a functional block diagram illustrating an example of acomputer system suitable for some aspects of embodiments of an automaticvoltage regulator.

Note that the same numbers are used throughout the disclosure andfigures to reference like components and features.

DETAILED DESCRIPTION

The subject matter of embodiments of the present invention is describedhere with specificity to meet statutory requirements, but thisdescription is not necessarily intended to limit the scope of theclaims. The claimed subject matter may be embodied in other ways, mayinclude different elements or steps, and may be used in conjunction withother existing or future technologies. This description should not beinterpreted as implying any particular order or arrangement among orbetween various steps or elements except when the order of individualsteps or arrangement of elements is explicitly described.

According to one aspect of the present invention, a frequency synthesistechnique is utilized to perform automatic voltage regulation tomaintain the output voltage, rapidly recover from voltage drops due toheavy transients, and maintain a voltage to frequency (V/Hz) ratio undervarying output loads. In one aspect of the frequency synthesistechnique, a higher multiple frequency of a reference signalcorresponding to the generator's desired output frequency is producedand phase locked to the reference signal by the use of a Phase Lock Loop(PLL) in conjunction with a frequency divider. The higher frequencysignal is a multiple N of the reference frequency, where N is thedivision factor of the frequency divider. In one example, to regulate agenerator configured to operate at 60 Hz, the frequency of the voltagecontrolled oscillator (VCO) of the PLL is 240 Hz and N is 4. FIG. 16 isan oscillogram illustrating the relationship between a line sync signalVLS (upper trace) and the PLL frequency (lower trace) in this example.

The frequency of the output voltage of the generator is obtained bysampling the output voltage, such as with a transformer or other linesensing circuit. The sensed output voltage frequency is then compared toa reference voltage VREF, which is a stable temperature compensated DCvoltage reference. In the examples described below, VREF is fixed at 6.8Volts, but other reference voltage levels may be utilized in otherembodiments without departing from the teachings of the presentinvention. The output of the comparator is the line sync signal (VLS),which is a square wave signal that is in phase with the output voltageof the generator. The VLS signal produced is a fast, clean and in-phasesquare wave AC voltage signal representing the generator's output phase.This signal is fed into the PLL voltage comparator to produce a flexibleVolts/Hz capability that stems from using the PLL as a frequency tovoltage converter.

This PLL based frequency synthesis technique can reduce delay in theresponse of the AVR to transient conditions in the output voltage toimprove recovery from transient conditions. The frequency synthesistechnique may also permit a higher chopper frequency to be used in a DCmodulator circuit that drives a power section to produce the fieldcurrent in the field winding of the generator rotor, which may furtherreduce feedback delay in the AVR. The frequency synthesis technique mayalso produce a feedback control signal with a reduced noise level, suchas the example shown in FIG. 19, which facilitates the introduction ofderivative feedback. Note that in some high power applications, a threephase, full wave, one or two quadrant, depending upon the operationalrequirements, SCR bridge rectifier circuit may be employed in place ofthe chopper circuit. Response time may increase, e.g. 2.8 msec versus 1msec, for the chopper function and the response may be less linear, butthe long time constants generally associated with large, high powermachines may permit such a substitution without departing from theteachings of the present invention.

FIG. 3 is a block diagram that illustrates one embodiment of asimplified AVR circuit 100 illustrating some aspects of the presentinvention. The output voltage of the generator VGEN is input to DC powersupply circuit 102, which then generates: a DC supply voltage VDC topower components in AVR circuit 100; a stable DC reference voltage VREF;and a full wave rectified signal VRS that reflects VGEN.

The output voltage of the generator VGEN is also input to samplingcircuit 110, which samples the output voltage VGEN and compares it toVREF in order to produce line sense voltage signal VLS, which representsthe frequency of VGEN. The output of the comparison is a square wavesignal that is in phase with VGEN. FIG. 4 is a graph illustrating thesignal waveform of VLS in response to oscillations in VGEN with respectto VREF, which is 6.8 V is the example shown.

VLS and VRS are input into PLL circuit 112 of FIG. 2, which uses VLS toidentify the peaks in VRS and sample the magnitude of those peaks inorder to produce control signal VCONTROL, which represents the absolutemagnitude of the voltage of VGEN. Note that VCONTROL is a DC levelsignal that can be compared to the DC reference voltage VREF in order togenerate a clean and precise error signal, which is important forregulating under heavy transient overloads to improve the transientresponse of the AVR control loop.

PLL circuit 112 also produces phase error voltage signal VOP, which isthe output from a voltage controlled oscillator (VCO) in the PLL andrepresents a highly responsive voltage to frequency conversion signalthat reflects variations in the frequency of VGEN. VOP may betransformed into a voltage to Hertz control signal VVH that engages whenthe frequency of VGEN drops below a selected threshold, e.g. the 60 Hzoperating frequency, to increase the frequency back to the selectedoperating frequency.

VCONTROL, VREF, VVH and a damping signal VDAMP are all input to erroramplifier 116, which subtracts the VCONTROL, VVH and VDAMP voltages fromVREF in order to produce an error voltage signal that is amplified andoutput as a duty cycle modulator control voltage VDCMOD. The voltagelevel of VDCMOD is input to duty cycle modulator circuit 120, which mayalso be referred to as a chopper. The voltage level of VDCMOD controlsthe duty cycle of a square wave signal having a predetermined frequency,e.g. 1 KHz, that is output as VFIELD. VFIELD drives power section orexciter 130 to produce IFIELD, which is the current in the rotor fieldfor generator 140. VFIELD is fed back through stabilizer 122 to producethe damping signal VDAMP, which is an internal negative feedback paththat dampens the level of modulation to maintain the stability of thecontrol loop.

For automatic voltage regulation, if the voltage of VGEN drops, such asdue to introduction of a heavy transient load, then the peak magnitudesof VRS will drop, which is sampled by PLL circuit 112 and reflected inthe voltage level of VCONTROL. This, in turn, will impact the voltagelevel of VDCMOD causing the duty cycle of VFIELD to increase, therebyincreasing the field current IFIELD, which, in turn, increases thevoltage level of VGEN. As the voltage level of VGEN returns to itspreselected level, e.g. 120 VAC, as reflected by VRS, VCONTROL willreturn to its steady state level causing VDCMOD to return to steadystate and reducing the duty cycle of VFIELD to its steady state level.

Likewise, for frequency control, if the frequency of VGEN drops, thiswill be reflected in the voltage level of the phase error signal VOP. Ifthe frequency drop exceeds a preselected threshold, then voltage toHertz circuit 114 will modify the voltage level of VVH, which will causeerror amplifier 116 to modify VDCMOD to decrease the duty cycle ofVFIELD and increase the frequency of the generator output voltage VGEN.As the frequency of VGEN returns to the selected operating frequency,VOP and, thus, VVH return to steady state levels resulting in VDCMODreducing the duty cycle of VFIELD to a steady state consistent with theoperating frequency.

In accordance with one aspect of the present invention, some embodimentsmay permit adjustment of the generator output voltage within a givenrange, typically +/−10% around a nominal voltage, i.e. 120 VAC line toground, and maintain the selected voltage in spite of load changeswithin a specified steady state regulation specification, such as below3%. This is achieved by generating a difference or error signal VCONTROLthat results from the difference between a reference DC voltage and thesampling of the output voltage of the generator.

In accordance with another aspect of the present invention, thegeneration of a fast responding clean error signal permits someembodiments of the present invention to regulate under heavy transientoverloads. The significance of a high quality error signal may beobserved from the basic relationship that links the error signal to theoutput voltage of the generator. In simplified form, this relationshipmay be expressed as: VGEN=H(s)*VERROR, where H(s) is the open looptransfer function for the combination of the error amplifier,demodulator, exciter, and generator components.

FIG. 5 is a block diagram illustrating in greater detail an example of atransfer function 150 representing a portion of the circuit of FIG. 3.At 152, the clean error signal VCONTROL obtained from sampling theoutput voltage VGEN is compared to the reference voltage VREF in orderto produce a voltage signal VERROR representing the difference betweenthe desired output voltage, which is determined by magnitude of VREF,and the actual output voltage of VGEN. Note that by changing VREF, thedesired output voltage for the generator system may be adjusted. Thisrepresents the outer control loop that provides proportional feedbackfor regulating the generator output voltage, and which includes theamplifier gain 154, the duty cycle modulator gain 156, the exciter'sgain and delay 160, the generator's gain and delay 162 and the sensor'sdelay 164. An inner control feedback loop introduces a stabilizer gainto produce VDAMP by introducing a zero to the transfer function.

In FIG. 5, the open loop transfer function, that is the TransferFunction with the proportional feedback or outer loop open can beexpressed as follows:

${H(s)} = \frac{{Ka}*{Kb}*{Kmod}*{Kex}*{Kgen}*( {I + {Td}} )}{( {I + {Te}} )( {I + {Tg}} )}$

wherein:

Te=Exciter's time constant;

Tg=Generator's time constant;

Ka, Kb=Gains of amplifiers in the error amplifier circuit;

Kmod=Gain of the duty cycle modulator;

Kex=Gain of the exciter;

Kgen=gain of the generator; and

Td is the zero that is introduced by the derivative feedback of theinner loop.

Td represents an amount of derivative control that used in proportion tothe ordinary proportional control provided by the outer loop and thatmay be adjusted.

Accounting now for the introduction of VDAMP to the summer 152, as wellas an optional VDROOP signal to control load current, VERROR can berepresented as follows:

V ERROR=VREF′−VCONTROL −V DAMP −V DROOP

Here, VREF′ is an adjusted value of VREF that results from the outputvoltage control. For an example, see the voltage signal VRO of the erroramplifier circuit 550 of FIG. 12, which is obtained by adjusting apotentiometer that is the generator output voltage control. In thisexample, VREF is a temperature compensated voltage reference of 6.8Volts. In addition, it is assumed, in this example, that the timeconstants associated with the error amplifier and power sections arewell below time constants Te and Tg. Examples of reference valuesreflecting these assumptions is, in milliseconds, 70<Te<500 and400<Tg<1000. Table 1 below illustrates an example of the gaincalculations to achieve a 1% steady state regulation specification:

TABLE 1 Steady State Regulation Calculations Units Required RegulationNo load to Full load 1% Max Peak Output Change 120 VAC 1% Regulation1.70 Volts Proportional feedback loop constant “Ksensor” 0.032 MaximumField excitation Voltage 100.0 Volts Error signal magnitude at 1%Regulation 0.055 Volts Total Gain required 1831 DC Modulator gain at 160V max output 64 chopper voltage, DC = 1 Required Combined ErrorAmplifier Gain 35 Chosen Combined Gain for error amplifiers 36

VDAMP is a voltage signal corresponding to the derivative of anattenuated voltage, where Kd is the attenuating constant in thisexample, that feeds the field of the exciter VFIELD. For example, theerror amplifier circuit of FIG. 12 shows VFIELD passing through anadjustable attenuation network in order to produce VDAMP. VDROOP is anoptional signal voltage that is a function of the output current of theoutput generator and is included here to demonstrate how droop controlmay be readily added to the circuit.

From the Transfer Function of FIG. 5, it may be observed that if theVERROR signal is zero, then no excitation will be available to theprimary field of the exciter. In order to maintain regulation at steadystate, the combined gain of the error amplifier and DC Modulatorcircuits is relatively high. The reference values provided in FIG. 5 andTable 1 above illustrate one example of values that produce sufficientgain for sufficient steady state operation.

In FIG. 5, the outer loop from the generator output through frequencysynthesis transfer block 164 to summer 152 provides ProportionalFeedback from the sensed generator output, which results in generationof VCONTROL. The error signal VERROR that results from the proportionalfeedback is a clean DC level signal. The inner loop from the output ofDC modulator 156 through stabilizer block 158 produces the VDAMP signal,which is subtracted at summer 152 and provides Derivative Feedback fromthe field voltage VFIELD. The amount of derivative feedback iscontrolled by adjusting the value of Kd in stabilizer block 158, whichalso adjusts the value of Td as discussed above. This is commonly knownas Damping Control in commercial AVRs. In the example discussed herein,the DC modulator block 156 is implemented as a chopper that operates at1 Khz and is driven by a duty cycle modulator circuit. For example, asillustrated in FIGS. 11 and 14, the chopper 540 is an Insulated GateBipolar Transistor (IGBT) or Power MOSFET (e.g. IRF740) that is drivenby a Duty Cycle modulator chip 520 (e.g. LM3524D). The resulting choppersignal is a modulated square wave signal VFIELD, which drives theexciter's field. The higher chopper frequency in this example, whencompared to standard 60 Hz Phase Control silicon controlled rectifier(SCR) circuits, provides for a smoother Field current waveform andminimizes the time delay associated with the power section. For example,the time delay with the IGBT chopper 540 at 1 khz will be less than 1milliseconds (msec). For a Full Wave single phase SCR phase controlcircuit, the delay could be as high as 8.3 msec.

In order to generate the VCONTROL signal, the examples herein sample thepeaks of the full rectified output voltage of the generator's outputvoltage. In the detailed example described herein with respect to FIG.8, the output voltage is sampled through a transformer 302 followed by atwo resistor network (RI and R2) that yields a peak voltage of 6.8V asthe peak voltage of VRS from a generator output voltage VGEN of 120 VAC.The sampling of the full rectified peaks is accomplished by applying asampling pulse that is synchronized with the peaks and is applied to aSample and Hold circuit, such as the sample and hold circuit 600 shownin FIG. 13.

In the example of FIG. 13, a pulse is generated in response to V_(Q1)and closes switch Sw1 for the length of the pulse (i.e 100 μsec). V_(Q1)passes through a sample pulse generation circuit 610 that has parallelsignal pathways each constructed using NAND gates and high pass filters,wherein the received V_(Q1) pulse travels at different speeds througheach signal pathway. The difference in propagation time through thesignal pathways results in a 100 microsecond pulse in the VQS signalthat is synchronized to the peak of the VRS signal. The VQS signaldrives switch Sw1 in holding circuit 620 to close for 100 microsecondsto sample the VRS signal, which is a DC signal that is held in capacitorC23 and produces VCONTROL.

In this example, the Sample and Hold (S/H) circuit 600 is sampling thepeaks for 100 microseconds (μsecs) and holding the sampled value for 8.3milliseconds, i.e. 180 degrees or half a cycle at 60 Hz, until anotherpeak arrives. The resulting VCONTROL signal for a constant generatoroutput voltage will be a substantially stable DC voltage level. Voltagevariations in the generator output voltage level, in this example, aresampled and updated every 8.3 milliseconds. FIG. 6 is a waveform diagramthat illustrates the sampling pulses produced in sampling signal VQS inresponse to V_(Q1). As FIG. 6 illustrates, the rectified voltage signalVRS is sampled for 100 μsec at the peaks of the VRS signal and held for8.3 msec. In practice, the VRS waveform may become distorted due to thesampling circuitry, such as a sampling transformer. However, thetransient performance of an AVR in accordance with certain aspects ofthe present invention would not be significantly affected because thesampling of the rectified output voltage VRS occurs for a relativelysmall interval of time at substantially the peak of the voltagewaveform. As a result, the control signal VCONTROL is resistant todistortion, such as the harmonic distortion introduced by a samplingtransformer or the generator's output voltage. Predictable sources ofdistortion can be offset by adjusting the output voltage control VRO,which is set at 6.8 Volts in this example, to compensate for thedistortion. A voltage change at the generator's output will change theDC level of VCONTROL.

In this aspect of the present invention, the approach to designing theTransfer Function is to reduce the time response associated with the AVRcontrol circuitry in the proportional feedback control loop to besubstantially less, e.g. by a factor of approximately 10 to 40 times,than the time constants associated with the Exciter (Te) and theGenerator (Tg). The error amplifier time constant, e.g. Ta and Tb,provide lead compensation to the error amplifier section. In thisexample, Ta corresponds to Amplifier 560 and Tb corresponds to Amplifier570 in the error amplifier 550 of FIG. 12. Tcs and Tcd correspond to lowpass filters in the derivative feedback network 580 of FIG. 12 and aresignificantly less than Te and Tg and are for the purpose of filteringout noise, which provides a clean damping signal VDAMP at the summingnode.

The sensor time constant Td has a delay of less than 8.3 msec. Thisremoves a root of the characteristic equation normally associated withthe voltage sensor and replaces it with a 8.3 msec time delay. The useof time delays in transfer functions is understood by those of skill inthe art. Hence, the complete Transfer Function M(s) for an AVR inaccordance with an aspect of the present invention can be described interms of H(s), as defined above, as follows:

M(s)=H(s)/(1+H(s)K SENSOR *e ^(−τds)),

where τds represents the maximum time delay resulting from the frequencysynthesis and sample and hold circuits described herein.

The response of the AVR is fast enough to produce the damping controlsignal VDAMP generated in the error amplifier circuit 550 shown in FIG.12. VDAMP improves the stability margin by adding a zero in the transferfunction. Those of skill in the art will understand the use ofderivative feedback effect to a closed loop transfer function tocompensate for the roots introduced by Te or Tg, which typically havetime constants on the order of 70 to 500 msec and against thedisturbances introduced by load changes thus maintaining stability. Forexample, see Kuo, Benjamin, Automatic Control Systems, 3d Edition 1975;Vleeshouwers, Derivation of the Model of the Exciter for SynchronousMachine, Einhoven University of Technology EUT Report 92-E-258, June1993; Glover et al., Power Systems Analysis and Design, 3rd edition,Brooks/Cole (2002).

FIG. 7 is a block diagram illustrating one example of an automaticvoltage regulator circuit 200 in accordance with the present invention,which is configured to regulate an output voltage VGEN of a generatorelectrically coupled to the AVR 200 by controlling the current providedto a field winding 240 for the exciter of the generator.

A DC voltage power supply 202 is configured to receive VGEN and producea 12 volt DC regulated supply voltage, which is the power supply toother components in AVR 200, full wave rectify VGEN to produce rectifiedvoltage signal VRS, and produce a stable reference voltage VREF, whichis 6.8 V in this example and is corresponds to the steady stateoperating voltage level of VGEN for which AVR 200 is designed. Othersteady state operating voltage levels may call for different referencevoltage levels. A line sampling circuit 210 is also configured toreceive VGEN and compare it to VREF in order to generate line syncsignal VLS, which is a square wave with pulses synchronized to theoscillation of the generator output voltage VGEN. FIG. 8 shows anexample of a detailed embodiment of the circuitry for DC power supply202 and line sampling circuit 210.

Quadrature signal generator circuit 220 includes a phase locked loop(PLL) circuit that locks onto the frequency of line sync signal VLS and,using a lock frequency that is a multiple of the desired generatorfrequency, produces a pair of square wave signals VΦ1 and VΦ2 that are90° out of phase with one another and synchronized with VLS. Quadraturesync circuit 222 uses VΦ1 and VΦ2 to generate a quadrature signal V_(Q1)that is in quadrature with VLS, i.e. phase shifted by 90°. V_(Q1) is asquare wave signal aligned to the peaks of the generator output voltageVGEN. V_(Q1) is fed to sample and hold circuit 226, which transformsV_(Q1) into a short duration pulse, e.g. 100 μsec, aligned with thepeaks of the generator output voltage VGEN that sample and hold circuit226 uses to sample the peak voltages of the rectified voltage signalVRS, which represents the absolute magnitude of VGEN. Sample and holdcircuit 226 samples the peaks of VRS and outputs generator controlsignal VCONTROL, which is a DC voltage signal that represents thecurrent voltage level of VGEN. FIG. 17 is an oscillogram illustratingthe relationship between VLS (upper trace) and V_(Q1) (lower trace) inthis example.

Quadrature signal generator circuit 220 also outputs a phase errorsignal VOP from the PLL that is an error output voltage signal thateffectively converts the phase difference between the VLS signal and theoscillating frequency of the PLL to a voltage signal that can be used byVoltage to Hertz control circuit 224 to control the frequency of thegenerator. Voltage to Hertz control circuit 224 utilizes the DC phaseerror signal VOP and utilizes the reference voltage signal VREF toproduce a voltage to frequency control signal VVH that represents aphase correction needed to maintain the desired frequency of VGEN.

Error amplifier section 230 receives DC voltage signals VCONTROL, VVH,VREF and damping feedback voltage VDAMP. Error amplifier 230 subtractsVCONTROL, VVH and VDAMP from VREF, which determines the desired outputvoltage level, in order to produce duty cycle modulation signal VDCMOD.Note that droop control may be readily obtained in this example byproviding a DC voltage signal for droop control that is also summed inerror amplifier 230. VDCMOD is a DC voltage control signal that reflectsthe reference voltage selected to determine the desired output voltagelevel of VGEN, the voltage level of VGEN sensed at the generator output,the phase of the sensed voltage signal, and damping control forstability. At steady state, these voltage signals will remainsubstantially stable.

VDCMOD drives duty cycle modulator 232, which, in this example, includesan oscillator that provides a chopper frequency, e.g. 1 kHz, used toproduce field voltage control signal VFIELD. VFIELD is a square wavesignal oscillating at the chopper frequency where the duty cycle of thesquare wave is controlled by VDCMOD. For example, when output voltagelevel of VGEN drops, e.g. in response to introduction of a transientload, this impacts VCONTROL and, in turn, causes VDCMOD to increase theduty cycle of VFIELD. The increased duty cycle of VFIELD increases thecurrent in the field winding 240 of the generator causing the outputvoltage level of the generator to increase. Similarly, if the frequencyof VGEN drops, then this will be reflected in VVH, which will causeVDCMOD to decrease the duty cycle of VFIELD, which also increases thefrequency of VGEN in order to maintain the output frequency. VDAMPprovides an internal stabilization control for the AVR circuit. Powersection 234 includes high current devices that converts VFIELD into thefield current in field winding 240.

Synchronization is important for sampling the voltage level of VGEN sothat the sampling pulses are substantially aligned with the peaks ofVGEN, as represented in absolute terms in VRS. To maintain accuracy,synchronization should be maintained even in the event that thegenerator's output voltage changes in frequency, which often occurs whena transient load is introduced. In the present example, the samplingpulses of VQS are generated using a signal that is 90 deg out of phasewith VLS. This signal is the quadrature signal of VLS and is labeled VQ.In an example of an implementation of quadrature synchronization circuit222 shown in FIG. 10. Output frequency tracking capability is used tomaintain a 90 degree phase shift between VLS and VQ to maintain theaccuracy of sampling of the peaks of VGEN. FIG. 18 is an oscillogramillustrating the relationship between VGEN, which is represented by thesinusoidal trace, and a quadrature sampling signal, which is representedby the trace with sampling pulses aligned to the positive and negativepeaks of VGEN.

In the present example, the frequency synthesis approach permits thegeneration of a square wave signal that is synchronized with the outputvoltage of the generator at four times the frequency. This is the outputVΦP of the voltage controlled oscillator (VCO) of PLL circuit 410 in oneimplementation of quadrature signal generator 220 that is shown in FIG.9. The PLL circuit 410, which is an IC 4046 in this implementation,tracks the frequency and phase of the incoming signal VLS so that theoutput of the VCO is in phase lock at four times the frequency of VLS.FIG. 16 is an oscillogram illustrating the relationship between VLS andthe PLL output, wherein the upper trace represents VLS, which is a 60 Hzline signal in this example, and the lower trace is PLL output OUT VCOobtained at pin 4 of the PLL IC 410, which is a type 4046 integratedcircuit for a phase locked loop with voltage controlled oscillator inthis implementation. A 240 Hz PLL signal (4×60) is in lock with the 60Hz signal. In this implementation, PLL Lock was tested to 30 Hz (120 HzVCO frequency) and showed a linear characteristic in V/Hz.

Quadrature Generator circuit 430, which is a type 4013 IC in thisexample, is a dual D flip flop connected so as to convert the 240 Hzsignal output by the VCO to two 60 Hz signals VΦ1 and VΦ2 that areseparated by 90 degrees and are fed to the Quadrature Sync Circuit 222.Quadrature Sync Circuit 222 transforms these signals into V_(Q1), whichis a signal separated by 90 degrees (e.g. quadrature) from VLS. FIG. 10illustrates an example of one implementation of quadrature sync circuit222. The relationship is illustrated in the oscillogram of FIG. 17,wherein the upper trace is VLS and the lower trace is V_(Q1). Quadraturesignal V_(Q1) is separated by 90 deg from VLS, even if the frequencychanges, so long as the PLL 410 in FIG. 9 holds lock.

The V_(Q1) signal is input to Sample and Hold circuit 226, an exampleimplementation of which is illustrated in FIG. 13. In FIG. 13, V_(Q1) ispassed through two separate signal paths, where each path has a highpass filter, which are implemented by capacitor and resistorcombinations C21/R59 and C22/R60. The second high pass filter C22/R60delays the edge with respect to the edge passing through the first pathfilter C21/R59 and into a set of NAND gates that transform the twodelayed signals into a short duration switching pulse in VQS. VQScontrols a CMOS switch Sw1, implemented using a type 4066 IC in thisexample, which samples the rectified output voltage signal VRS at eachpeak, in this example, and holds the sampled DC voltage level using acapacitor C23 to produce the VCONTROL signal.

The VQS signal produced by the NAND gates 610 is a series of pulses thatare synchronized to the output voltage VGEN even if the output frequencyvaries with the top and bottom peaks of the generator's output voltage.FIG. 18 is an oscillogram illustrating the relationship between the linevoltage VGEN, which is the sinusoidal trace, and the sampling pulses,which appear as spikes aligned with the peaks of the line voltage.VCONTROL is the result of synchronized sampling of the peaks of the fullwave rectified generator's output voltage VRS. The synchronized pulsesare thus applied to the sample and hold circuit of FIG. 13 in order toproduce a DC voltage signal VCONTROL that represents the peak voltagelevel of the generator's output voltage VGEN, which is substantiallylevel when VGEN is a constant voltage. In this example, VQS samples VRSevery 8.3 msec.

The resulting control voltage VCONTROL, obtained in accordance with thepresent invention, exhibits far less ripple voltage than the signalobtained from many conventional rectified RC type AVRs. FIG. 19 is anoscillogram that compares the control voltage obtained using aconventional approach utilizing full wave rectification with an RCfilter with a 20 msec time constant versus the frequency synthesisapproach of the present invention. In this example, the conventionalsignal is illustrated by the upper trace of the oscillogram and isessentially a saw tooth waveform. The upper trace shows a single phasefull wave rectified and filtered 5V DC voltage with a 1.8 V peak to peakripple. The level line of the lower trace of the oscillogramdemonstrates an example of the VCONTROL signal obtained in accordancewith the present invention when the output voltage of the generator VGENis at steady state. Note that VCONTROL, in this example, is a constant 5VDC signal that does not exhibit the ripple that is present in theconventional control signal in the upper trace.

The sampling signal V_(Q1) is in quadrature synchronization with VLS,which, when fed through the sample and hold circuit of FIG. 13 obtains astable, low noise voltage signal that is updated twice in every cycle ofVGEN. That is, at 60 Hz generator output frequency, the VCONTROL signalis updated every 8.3 milliseconds in the case of single phase sampling,which produces a high quality control signal compared to conventionalAVR approaches that utilize full wave rectification with an RC filter.The VCONTROL signal accurately represents the amplitude of the peaksoutput by the generator and is updated every half a cycle (e.g. 8.3 msecat 60 Hz) even if the frequency drifts so long as synchronization ismaintained. Hence, it represents a time delay that will result in aphase shift in the Transfer Function. This phase shift will be smallgiven the fact that the frequency response of the Exciter/Generator istypically close to two decades below 120 Hz. For illustrative purposes,a typical Exciter field time constant is 80 msec and the frequencyresponse of the exciter is 2 Hz, and the phase shift is 6 degrees at agenerator's voltage output frequency of 60 Hz. (See VleeshouversEindhoven University of Technology EUT report 92-D-258.)

Once phase lock on the generator output signal is obtained, the VCO willproduce a voltage signal that will change linearly as a direct functionof the frequency of the generator output voltage VGEN. Hence, aFrequency to Voltage characteristic is achieved that can be readilyutilized to produce a flexible Voltage to Hz control signal, as will nowbe discussed.

Volts per Hertz (V/Hz) control section: The PLL design shown in FIG. 9exhibits a voltage to frequency conversion of 80 mV/Hz in the Vop signaloutput by the VCO of PLL circuit 410. The Vop signal that the PLLgenerates is an output voltage signal that is a linear function of thereference frequency. This frequency/voltage conversion property of Vopcan be readily applied to obtain a control characteristic that maintainsa constant Volts/Hz ratio in spite of frequency variations, thusavoiding saturation of the electromagnetic components of the load.Preferably, this characteristic has an adjustable start frequency (i.e.the maximum frequency at which the V/Hz starts) from a maximum of 60 Hzto a minimum that is the lowest frequency expected during overloadconditions.

It is also useful to provide a flexible Volts/Hz capability that can beadjusted so as to best assist the recovery of the primemover/exciter/generator combinations in the case of a heavy transientoverload. For example, it is useful to provide the ability to adjust theV/Hz ratio from 1:1 to a higher value so that the output voltage willdrop faster as the prime mover speed decreases as a result of atransient overload. Additionally, the flexible Volts/Hz controlcapability may provide the ability to control the frequency at which theV/Hz ratio begins to adjust at a predetermined frequency below 60 Hz(usually between 59.5 Hz to 57 Hz) so as to provide effective regulationfor light to moderate load changes.

FIG. 15 is a circuit diagram illustrating one example of a voltage tohertz control circuit 700 in accordance with certain aspects of thepresent invention. PLL VCO input voltage Vop from PLL circuit 410 inFIG. 9, which is the filtered phase error signal output by the phasedetector of PLL circuit 410, is input to a voltage follower amplifier710, which is a CA 3140 high impedance operational amplifier in theexample of FIG. 15 and which reduces the loading on the VCO output. Theoutput Vo′ of the voltage follower amplifier 710 is input to a voltageamplifier 720 with gain that is adjustable using variable resistor Rh.The signal input to voltage amplifier 720 is the difference between theoutput of the voltage follower LM358 730, which supplies a calibratedvoltage Vk that is adjusted by variable resistor Ra, and the adjustedphase error output Vo′ from voltage follower amplifier 710. Vk is afrequency reference voltage corresponding to a desired oscillatingfrequency that is fed into a voltage follower amplifier 730, in order toavoid loading the frequency reference voltage Vk, and produce acalibrated voltage reference. In the example shown, Vk is set to 6.2 Vand the output of the VCO in PLL 410 of FIG. 9 is also adjusted to 6.2 Vby variable resistor VRf. The circuit is thus calibrated to 60 HZbecause the reference voltage Vk is the same as the VCO output voltageVΦP so that the voltage at the input of voltage amplifier 720 is zero.

As the frequency of VGEN decreases, so does the voltage that is input tothe voltage amplifier 720 and its output decreases the reference voltagefed to the control loop of FIG. 5, which decreases the output voltageVGEN of the generator. The sharpness or slope of the decrease isadjusted by adjusting resistor Rh. At Rh=0, the V/Hz ratio is 1:1. At Rhmaximum, in this example, the ratio is 1:2.6. These values may beselected by design criteria to obtain the V/Hz ratio for the desiredrange of performance.

To adjust the frequency at which the V/Hz Characteristic is applied, aCMOS switch Sw2 is utilized at the output of amplifier 720. If switchSw2 is disconnected, then the V/Hz functionality is disabled. When Sw2is closed, the V/Hz control functionality will take effect with the V/Hzrelationship determined by Rh, as explained above. The switch Sw2 iscontrolled by switching voltage signal Vsw that is the output of voltagefollower amplifier 732, which is implemented as amplifier 730 in thesame LM358 integrated circuit in the example shown, so that the sectionworks as a voltage comparator. This comparator compares the VCO inputvoltage (Vo′) with a voltage reference that is adjusted by a 10Kpotentiometer. The potentiometer has an adjustment range of 0.4 V sothat an adjustment range of 5 V is obtained with a V/Hz characteristicof 0.08 V/Hz. When V/Hz control circuit 700 is calibrated as describedabove, the V/Hz functionality can be controlled to engage at anyselected frequency between 60 Hz and 55 Hz. Again, this range may bemodified, but it is sufficient for a 60 Hz generator since it's unlikelythat the frequency of output voltage VGEN will drop below 55 Hz undernormal operating conditions. In this example, the voltage to hertzcontrol circuit 700 provides a flexible V/Hz control functionality thatmay be adjusted from a ratio of 1:1 to 1:2.6. Circuit 700 can beconfigured to activate in at a selected frequency from 55-60 Hz. The1:2.6 V/Hz selection combined with a sharp voltage drop per Hz assiststhe recovery of the frequency of the prime mover of the generator.

In this example, the circuit is implemented using standard CMOSintegrated circuits for the digital portion, such as the quadraturegenerator circuit 400 of FIG. 9 and the sample and hold circuit 600 ofFIG. 13. Analog circuitry is used to implement the V/Hz control circuit700 of FIG. 15 using standard operational amplifiers. The DC modulatoror chopper circuit 650 of FIG. 14 utilizes a LM3524D integrated circuitthat is specifically designed for use in switching power supplies. TheLM3524 circuit provides a linear characteristic for duty cyclemodulation from 1% to 98% responsive to the VDCMOD voltage output fromerror amplifier circuit 550 of FIG. 12, where VDCMOD ranges from 1 voltto 3.5 volts. The control voltage range of 2.5 volts when the DCmodulator circuit 650 has a duty cycle of 1 defines the gain of the DCmodulator circuit 650. For example, a 160 volts maximum output with a2.5 volts input range implies a gain of 64. In order to obtain a rapidtransient response, this example utilizes the clean and fast respondingdetection signal to produce an error signal VDCMOD that is used tocontrol an Insulated Gate Bipolar Transistor (IGBT) in the DC modulatorcircuit 650. The DC modulator circuit 650 operates at a frequency ofapproximately 1 Khz, which is well above the 60 Hz frequency of thepower generator.

DC modulator circuit 650 utilizes linearly controlled Duty Cyclemodulation in order to control the Field Current of field 240 in FIG. 7.This approach provides improved linearity compared to conventional SCRphase control techniques. Also, the higher DC modulator frequencycombined with the fact that the voltage signal that is supplied is DCcapacitor filtered voltage provides a much smoother field current.Further, the low noise detection signal minimizes jitter or blinkingassociated with no load or very light load conditions thus reducingdamping requirements for addressing the jitter. The DC voltage supplyobtained from a 120V AC full wave rectified and filtered AC voltageprovides 160V DC, which may provide higher field current and, therefore,more field force as compared to a conventional full wave unfilteredsupply. For example, a conventional 120 VAC full wave unfiltered supply,which is normally used with a SCR phase control based system, wouldsupply 100V DC to the Exciter's field. The filter capacitor may beeliminated in some embodiments designed for higher power and/or voltageratings that utilize a three phase full wave rectifier to feed the DCmodulator.

In the power circuit 500 embodiment shown in FIG. 11, a relay with aninitial delay may be used to feed an IGBT 540 in order to supply initialcurrent to the field winding 530. An initializing circuit may be used insome embodiments to maintain the output voltage oscillating betweenaround 130 to 135V AC until the PLL locks and takes control, whichtypically occurs in approximately 5 seconds. Once initialized, thegenerator supplies the voltage selected with the voltage adjustmentcontrol. Short circuit protection is provided for the IGBT 540 by adesaturation technique that may disconnect the IGBT in less than 8 μsecin case of a stiff short. The short circuit protection combined with astandard circuit breaker, e.g. a 5 A circuit breaker, generally providesadequate protection to the automatic voltage regulator circuit. Theexample shown in FIG. 11 is designed to supply up to 5 Amps continuouscurrent at 40 degrees C. ambient temperature. The performance isgenerally limited by the capacity of a heatsink thermally coupled to thecircuit. The power circuit 500 generally dissipates 4.5 W/Amp of outputcurrent.

The design as described above allows for self-starting based on residualmagnetism with a minimum voltage of 4 VAC at the generator's output,which is a common requirement for emergency diesel driven generators. Itis noteworthy that the starting relay is not required to handle highvoltages or currents regardless of the current rating output of the AVR.Calibration upon construction and/or repair can typically be made with afour digit digital multi-meter with a 0.5% precision in DC voltagemeasurement, which facilitates device production. Instruments aregenerally not needed when an AVR is installed since only the outputvoltage and damping are typically adjusted.

As a result of the frequency synthesis technique of the presentinvention, the output of error amplifier sections 116 and 230 at steadystate is essentially a constant 6.2 V DC voltage with no significantripple in the examples discussed above. The duty cycle modulationcontrol signal VDCMOD feeding the Duty cycle modulators 120 and 232 willalso be an essentially constant average value, which leads to the fieldcurrent provided to the field winding for the generator being constantand substantially ripple free.

FIGS. 20 and 21 are oscillograms illustrating an example of transientresponse for a simulation in accordance with one example of the presentinvention when the load on the generator output jumps from 2% to 93% ofmaximum generator capacity. The upper trace of FIG. 20 represents theoutput at pin 6 of error amplifier 560 in FIG. 12, which is a relativelynoise free and fast responding error signal. The lower trace is theoutput of the chopper circuit, such as the circuit of FIG. 15, whichdrives the field of the exciter. When the chopper output in the lowertrace is low, then the full forcing voltage is being supplied to thefield winding. When the chopper output is high, no excitation is beingsupplied to the field, which is then flywheeling. When the transientload increase occurs, the VDCMOD signal goes low and then returns to itssteady state through a series of ramps, which causes the chopper outputto apply several bursts of pulses to the field in order to increase theoutput of the generator in response to the transient thereby stabilizingthe generator voltage. In the oscillogram of FIG. 20, the chopperresponse and field excitation occur with a delay of less than 1 msecbased on the error signal.

FIG. 21 is an oscillogram comparing the VDCMOD error signal (top trace)to the generator output voltage VGEN (lower trace). In FIG. 21, theerror signal has a delay of 8.3 msec or less and has low noise and theduty cycle of the field forcing is approximately 85% for the first 12milliseconds of the transient of the error signal shown in FIG. 20. Theexciter's field will be fully driven, e.g. 150 VDC, in less than 9.3msec after occurrence of the transient. The fast, low noise response ofthe error signal combined with the high level of field forcing leads toa rapid, well damped response of the generator output voltage.

The embodiments discussed herein are directed to sampling a single phaseof the output voltage VGEN. If greatly unbalanced loads are expected,then other embodiments can be designed such that three phases aremonitored and the resulting pulses combined at the Sample and Holdcircuit. This entails no additional complexity since it is merelyduplicating the line sampling and synchronization circuits three times.The sampling frequency for frequency synthesis is also tripled reducingthe delay associated with voltage sensing in the outer proportionalcontrol loop to 2.8 msec, i.e. 8.3 msec divided by 3. The additionalcost may be relatively modest since low cost, low power parts may beutilized.

Droop control may also be implemented at low cost in some embodiments byreducing the gain of the amplifier section, which increases the errorsignal in order to supply an incremental load and thus provide droopcontrol. This may lead to a degradation of the regulation specification.Droop control that does not compromise regulation performance and iscapable of improving the steady state regulation generally requiresprecise and fast measurement of the output current.

Embodiments of the AVR described above can be implemented thataccurately detect the magnitude of the peak value of an AC sinusoidalvariable signal and present it as a DC voltage level. By sampling theoutputs of each phase through the use of current transformers, the loadcurrent can be monitored as a DC voltage level with speed and precision,which allows the load current to be closely monitored. The DC levelsignals thus produced will accurately represent the magnitude of theoutput current.

The DC level current control signals may be combined in a circuit thatfunctions similarly to the Volts/Hz control circuit discussed above.However, while the slope is directly proportional for Volts/Hz control,i.e. the excitation drops as the frequency decreases, the slope isinversely proportional for Volts/Amps control, i.e. the excitation dropsas the current increases, so the circuitry is modified accordingly. Thiswill permit the current level at which the Droop control starts to beadjusted as well as the sharpness of the Droop control response as thecurrent output increases. Sampling and representing the output currentand output voltages as DC voltage levels allows for flexible control ofthe generator by adjusting the field excitation, which adjusts theVERROR equation above for summer 152 by including the VDROOP outputcurrent control. The DC levels can be readily combined in the summer toprovide a fast field excitation reduction when the predetermined currentcontrol limit is reached resulting in effective droop control. Instand-alone applications, the droop control can be adjusted so as tocancel the steady state 1% regulation drop by reversing the slope of theVolts/Amps characteristic as long as the output current rating of thegenerator is not exceeded.

It is noteworthy that A/D conversion of DC levels is verystraightforward if microprocessor control is utilized in implementationof the AVR. Further optimization may be accomplished throughmicroprocessor control using a look up table that includes specific datacharacterization, i.e time constants and Field Current versus Outputcurrent, of the specific synchronous generator and both the VREF and thedamping constant Kd may be adjusted in such embodiments in order toefficiently control a given Prime Mover generator setup by the AVR.

One of ordinary skill in the art will readily recognize that manyaspects of the AVR described herein may be implemented using digital ormicroprocessor based technology. FIGS. 22 and 23 are control flowdiagrams illustrating a microprocessor based implementation of the V/Hzcontrol and error amplifier sections, respectively, discussed above withregard to FIGS. 12 and 15. The digital embodiments shown utilizepersistent memory, such as read only memories (ROMs), to store operatingdata so that the data is preserved in the event. The memory may beimplemented using modifiable memory, such as electrically erasableprogrammable read only memory (EEPROM), in order to provide an abilityto modify and customize the operating data for a particular applicationor generator.

FIG. 22 shows an example of a voltage to Hz control function 800implemented in a digital circuit that includes a computational device,e.g. a microcontroller or microprocessor, to implement the V/Hz section224 of FIG. 7. FIG. 22 is a control flow diagram illustrating the stepsor stages of an exemplary process for voltage to hertz control that maybe performed in a digital embodiment of another example of an automaticvoltage regulator.

Quadrature signal generator circuit 220 also outputs a voltage signalVΦP from the PLL that is an error output voltage signal that effectivelyconverts the phase difference between the VLS signal and the oscillatingfrequency of the PLL to a voltage signal that can be used by Voltage toHertz control circuit 224 to control the frequency of the generator.Voltage to Hertz control circuit 224 utilizes the DC voltage signal Vopand utilizes the reference voltage signal VREF to produce a voltage tofrequency control signal VVH that represents a phase correction neededto maintain VGEN at the desired frequency.

At step 802, voltage signal VΦP from the PLL of quadrature signalgenerator circuit 220 is converted from analog to digital form. VΦP isan error output voltage signal that effectively converts the phasedifference between the VLS signal and the oscillating frequency of thePLL to a voltage signal that may be used to control the frequency of thegenerator. In one example, an analog to digital converter with ten bitresolution is utilized to accommodate an input range of 10 VDC, whichprovides an equivalent resolution of 0.12 Hz, with a sampling rate of200 microseconds so as to avoid excessive delay. In this example,calibration of the PLL results in VΦP being 6.2 V for a generatoroperating at a stable frequency of 60 Hz. In the example of FIG. 9, thesensitivity exhibited by the 4046 PLL circuit 410 is 80 mv/Hz. In orderto achieve a 1:1 voltage to frequency ratio, VΦP is scaled by 1.26 inthis embodiment. The result of the analog to digital conversion andscaling is a corresponding digital value VΦP.

V/Hz slope control is determined at step 804 by multiplying VOPG by aV/Hz slope parameter obtained from operational data store 810. In thisexample, the operation data parameters for the particular applicationare selected at step 812 through a user control input selection, whichincludes the V/Hz, Vk reference voltage, scaling factor N, thresholdfrequency Fth, and the generator output voltage selection Vr. Theselections may be displayed at step 814.

For this example, the V/Hz parameter selected is 1.26 and Vk is 1.2. Theresult of steps 804 and 806 is VOPG×1.26−1.2 to create Vf, which isscaled by N at step 808 to produce scaled frequency error signal NVf.The value of N is selected to determine the rate of the AVR's response.For example, the range for “N” may be from one to four. The V/Hz slopeparameter, in this example, ranges from 1:1 to 2:26 V/Hz. Greater rangesmay be provided in some implementations.

The frequency threshold Fth is also selected to determine the frequencyat which the AVR begins to apply the selected V/Hz slope. In thisexample, the selectable range for Fth is from 60 to 55 Hz with thecorresponding value for Fth stored in frequency threshold store 830 andthe values for Fth vary from 0 to 0.4 depending on the desired thresholdfrequency. The value of variable NVf is compared with the selected valuefor Fth at step 820. If Fth is not greater than NVf, then the V/Hz slopeis not applied and control branches to step 822, where the value offrequency control variable M is set to steady state reference value Vk,which corresponds to 6.2V in the present example for 60 Hz operation,such that no frequency adjustment is performed and control continues tostep 826. If Fth is greater than NVf, then the frequency controlvariable M is set to the value of Fth in order to engage frequencycontrol at the selected threshold frequency. In other examples, asimilar approach may be applied to an over frequency at which frequencycontrol is to terminate, e.g. 65 Hz.

At step 826, the value of M determined above is multiplied by the outputvoltage level parameter Vr, which defines the selected generator outputvoltage. For example, ten values may be stored in the VGEN selectionstore 832, e.g. a ROM or EEPROM, to permit the generator's outputvoltage to be selected from 110 VAC to 125 VAC in ten increments. Avoltmeter showing the generators output voltage through a digitaldisplay may also be included in some embodiments of an AVR.

The result from multiplying M×Vr at step 826 is digital frequencycontrol signal VVHD, which is converted from a digital to analog valueat 828 in order to produce frequency control signal VVH, which is outputto an error amplifier, such as the error amplifier shown in FIG. 12, asthe analog signal that is input to a potentiometer that control thegenerator's output voltage in the analog version shown. However, if theerror amplifier function is implemented digitally, as shown in FIG. 23,then the voltage of the generator's output is controlled by selecting agiven Vr value as explained above.

Note that, in some embodiments, it is possible to implement the PLLusing a number controlled oscillator (NCO) and digital filtering inplace of a VCO. Sampling rates will need to be high enough to ensure lownoise and jitter due to quantization error. The clock frequency usedshould be high enough to accommodate computation of the frequencysynthesis process with a delay of less than about 3 degrees at anoperating frequency of 60 Hz.

FIG. 23 is a control flow diagram illustrating the steps or stages of anexemplary process 850 that may be performed in a digital circuit thatincludes a processor or similar device to digitally produce an errorsignal in a digital embodiment of another example of an automaticvoltage regulator. In this example, the analog DC voltage level controlsignal VCONTROL output from the Sample and Hold circuit 600 of FIG. 13is converted to a digital equivalent value at step 852 to produceVCTRLD.

Note that the circuits that generate VCONTROL are a mixture of digitaland analog. The frequency synthesis and synchronization circuits as wellas the Sample and Hold circuit are digital, but the output VCONTROL is aDC voltage level that represents the magnitude of the generator's outputvoltage. In this example, the analog to digital conversion has ten bitresolution and a sampling speed of 200 microseconds. Longer samplingtimes will degrade the transient performance of the regulator. To reduceresponse time, separate microcontrollers may be utilized for the ErrorAmplifier and the V/Hz control process 800 of FIG. 22 in order toperform these processes in parallel and reduce execution time, thoughexecution may need to be synchronized. The speed issue may becomeimportant because a typical encoding algorithm for the Pulse WidthModulation (PWM) operates at 1 Khz with a Duty Cycle ranging from 1% to100% and time intervals as short as 10 microseconds may need to beaccommodated.

The VFIELD signal from the DC modulator circuit 650 of FIG. 14 isreceived and filtered at step 860. The filtering step may involve apotential divider circuit and a low pass filter with a zener diodeincluded for protection purposes. The filtering may also involve a 1Microfarad capacitor and 120K resistor that provide a derivative action.The analog to digital conversion performed at step 862 involves highinput impedance, in one example, in order to reduce the effect on thederivative action of the filter step 860. The input filtering anddividing function of step 860 is configured to provide an outputequivalent to the lowest setting of the damping adjustment control inthe analog error amplifier circuit of FIG. 12. Further, the filteringfunctionality of step 860 is selection to have time constants that areelectrically equivalent to the V/Hz control circuit 700 of FIG. 15.

At step 864, the conditioned and digitized VFIELD signal is multipliedby a damping factor D selected from damping factor store 870 by a userselection at step 872. The damping factor is selected by a user asneeded to compensate for loop stability and load disturbances. In oneexample, ten values for D ranging from 1 to 31.6 in ten evenly spacedincrements are stored in a ROM and selected by the user by a control,such as up down pushbuttons, with a display that indicates the valueselected, i.e. D=10 means multiply by 31.6. The result of themultiplication at step 864 is digital damping signal VDMO.

At step 854, VCTRLD is subtracted from VDMO and the result multiplied bya predetermined Gain value at step 856, in this example, where a Gainvalue of 40 is used, which is equivalent to the combined gain of theamplifiers in error amplifier circuit of FIG. 15. The output of gainblock 856 is then PWM encoded at step 858 to produce the VDCMOD signalthat is output to a duty cycle modulator, such as duty cycle modulatorcircuit 232, which, in turn, drives the power section 234 in order togenerate the field current IFIELD for the field winding.

FIG. 24 depicts a computing device 900 that includes a bus 910 that maydirectly or indirectly couple all or some of the following devices:memory 912, one or more processors 914, one or more presentationcomponents 916, input/output ports 918, one or more graphics processingunits (GPUs) 917, input/output components 920, and an illustrative powersupply 922. The bus 910 represents what may be one or more busses (suchas an address bus, data bus, or combination thereof).

Although the various blocks of FIG. 24 are shown with lines for the sakeof clarity, in reality, delineating various components is not so clear,and metaphorically, the lines would be more accurately be grey andfuzzy. For example, one may consider a presentation component such as adisplay device to be an I/O component. Also, processors have memory. Inaddition, GPUs can have their own internal busses and independent memoryto the main system memory. Not all of the components shown in FIG. 24are needed to implement certain aspects of the present invention. Forexample, if no display is implemented, then the presentation components916 and GPU 917 may not be needed. Likewise, if no input/outputfunctionality is implemented, then components 918 and 920 may not beneeded. Power supply 922 may be the same supply utilized to support theanalog components. And many of the components shown may be combined inmicrocontroller devices, which are suitable for certain embodiments ofcertain aspects of the present invention. One of ordinary skill in theart will readily recognize that a wide variety of devices and systemshaving processing capability may be utilized in certain embodimentswithout departing from the scope of the present invention.

The computing device 900 typically includes or can operate with avariety of computer-readable media. By way of example, computer-readablemedia may includes Random Access Memory (“RAM”); Read Only Memory(“ROM”); Electronically Erasable Programmable Read Only Memory(“EEPROM”); flash memory or other memory technologies; Compact DiscRead-Only Memory (“CDROM”), Digital Versatile Disks (“DVD”) or otheroptical or holographic media; magnetic cassettes, magnetic tape,magnetic disk storage or other magnetic storage devices, or any othermedium that can be used to encode and persistently store desiredinformation for a sufficient duration of time to allow the informationto be accessed by computing device 900 for use in certain embodiments.

The memory 912 includes computer-readable media in the form of volatileand/or nonvolatile memory. The memory 912 may be removable,non-removable, or a combination thereof. Exemplary hardware devicesinclude solid-state memory, hard drives, optical-disc drives, etc. Thecomputing device 900 includes one or more processors that read data fromvarious entities such as the memory 912 or I/O components 920.Presentation component(s) 916 present data indications to a user orother device. Exemplary presentation components 916 include a displaydevice, speaker, printing component, vibrating component, etc.

The GPU 917 is typically dedicated to processing and rendering datarelated to graphics, but can be manipulated to process other data andcommand types. GPUs 917 are often integrated into, or installed on apresentation component 916, such as a video card, or are integratedinto, or installed on a motherboard, main circuit board, or logic boardof the computing device 900. In an embodiment, the central processingunit, (“CPU”) provides the functions of a GPU 917 for the computingdevice 900. I/O ports 918 allow the computing device 900 to be logicallycoupled to other devices including I/O components 920, some of which maybe built in.

Note that in the analog example discussed above, output scaling was doneto accommodate the LM3424D circuit 660 of the Duty Cycle modulatorcircuit 650 of FIG. 14, which has an input range of 1 to 3.5 Volts inorder to obtain duty cycle control from 1% to 100%. In one example, thePWM encoding function 858 has to emulate the performance of the LM3424D.Alternatively, the input signal to PWM block 858 may be fed to a digitalto analog converter to convert it an analog voltage signal that may beinput to an LM3424D circuit.

Embodiments of an AVR as discussed herein may be implemented digitally.Digitization may also provide a means to display the values of the keyvariables under control, such as V/Hz slope, voltage threshold, damping,and output voltage. It may also provide for adjustment of thesevariables via a user interface, such as up down pushbutton functionalityor graphical user interface control, which may be readily implemented bywell-known user interface functionality. A digital implementation mayalso facilitate remote digital control of the AVR and display ofoperating parameters and data of a remote AVR.

The examples above demonstrate that a frequency synthesis approach toautomatic voltage regulation combined with sample and hold circuitry caneffectively capture and convert a peak value of an AC sinusoidalgenerator output voltage to an accurate DC voltage control with aresponse time of one half of the period of the frequency of thegenerator output signal being measured and regulated. This approachproduces a responsive, low-noise and precise error signal for aproportional control loop of an AVR. By using an IGBT or PMOS switchchopper, the time constants of the AVR and the time delay in signaldetection may be significantly reduced, e.g. by a factor of 10 to 40times, below the time constants typically associated with conventionalsynchronous generators. Significant improvements in responsiveness andprecision control in transient response may be achieved whilemaintaining stability and steady state regulation, e.g. approximately 1%no load to full load. Additionally, the frequency versus Hz linearcharacteristic readily available from the frequency synthesis approachlends itself to use as an effective and flexible implementation of aVolts/Hz control characteristic for handling heavy transient loads instand-alone generator operation. By monitoring the output currents usingfrequency synthesis, e.g. converting the peak values of the outputcurrents to DC voltage levels, an adjustable droop control may be addedto facilitate parallel generator operation as part of a power system.

It will be understood by one of ordinary skill in the art that, whilethe embodiments of the invention described herein are generally designedfor 60 Hz at 120 VAC line to ground and 208 VAC line to line voltagegenerator output, the invention can also be applied to operate at 50 Hzwith minor recalibration. Different voltages may be obtained by changingtransformer primary voltage ratings.

Additionally a selector switch may be added to select between 60 Hz and50 Hz. A wide range of embodiments of the invention maybe be implementedutilizing the power ratings of modern Power Semiconductors and oftransformer selection for different voltages (i.e. 120, 208, 440) VAC.

It should also be understood that the present invention as describedabove can be implemented in the form of control logic using computersoftware in a modular or integrated manner. Based on the disclosure andteachings provided herein, a person of ordinary skill in the art willknow and appreciate other ways and/or methods to implement the presentinvention using hardware and a combination of hardware and software.

Any of the software components, processes or functions described in thisapplication may be implemented as software code to be executed by aprocessor using any suitable computer language such as, for example,Java, C++ or Perl or using, for example, conventional or object-orientedtechniques. The software code may be stored as a series of instructions,or commands on a computer readable medium, such as a random accessmemory (RAM), a read only memory (ROM), a magnetic medium such as ahard-drive or a floppy disk, or an optical medium such as a CD-ROM. Anysuch computer readable medium may reside on or within a singlecomputational apparatus, and may be present on or within differentcomputational apparatuses within a system or network.

All references, including publications, patent applications, andpatents, cited herein are hereby incorporated by reference to the sameextent as if each reference were individually and specifically indicatedto be incorporated by reference and/or were set forth in its entiretyherein.

The use of the terms “a” and “an” and “the” and similar referents in thespecification and in the following claims are to be construed to coverboth the singular and the plural, unless otherwise indicated herein orclearly contradicted by context. The terms “having,” “including,”“containing” and similar referents in the specification and in thefollowing claims are to be construed as open-ended terms (e.g., meaning“including, but not limited to,”) unless otherwise noted. Recitation ofranges of values herein are merely indented to serve as a shorthandmethod of referring individually to each separate value inclusivelyfalling within the range, unless otherwise indicated herein, and eachseparate value is incorporated into the specification as if it wereindividually recited herein. All methods described herein can beperformed in any suitable order unless otherwise indicated herein orclearly contradicted by context. The use of any and all examples, orexemplary language (e.g., “such as”) provided herein, is intended merelyto better illuminate embodiments of the invention and does not pose alimitation to the scope of the invention unless otherwise claimed. Nolanguage in the specification should be construed as indicating anynon-claimed element as essential to each embodiment of the presentinvention.

Different arrangements of the components depicted in the drawings ordescribed above, as well as components and steps not shown or describedare possible. Similarly, some features and subcombinations are usefuland may be employed without reference to other features andsubcombinations. Embodiments of the invention have been described forillustrative and not restrictive purposes, and alternative embodimentswill become apparent to readers of this patent. Accordingly, the presentinvention is not limited to the embodiments described above or depictedin the drawings, and various embodiments and modifications can be madewithout departing from the scope of the invention.

What is claimed is:
 1. An automatic voltage regulator circuit, thecircuit comprising: a direct current power supply circuit configured toreceive a power signal to be regulated and, responsive thereto, fullwave rectify the received power signal and generate a DC referencevoltage signal, where a voltage level of the DC reference voltagecorresponds to a desired steady state operating voltage level for thepower signal; a line sampling circuit configured to receive the powersignal and compare the power signal to the DC reference voltage signalin order to generate a line sync signal synchronized to an oscillationfrequency of the power signal; a quadrature signal generator circuitconfigured to receive the line sync signal and produce first and secondphase signals that are synchronized to the line sync signal and 90° outof phase with one another, where the quadrature signal generator circuitincludes a phase locked loop circuit configured to lock onto thefrequency of the line sync signal using a lock frequency that is atleast twice the oscillation frequency of the power signal, where thephase locked loop circuit is configured to output a phase error signalthat corresponds to a phase difference between the line sync signal andan oscillating frequency of the phase locked loop; a quadrature synccircuit configured to receive the first and second phase signals and,responsive thereto, generate a quadrature signal that is in quadraturewith the line sync signal; a sample and hold circuit configured toreceive the quadrature signal and the full wave rectified power signaland responsive thereto, sample the peak voltages of the full waverectified power signal using the quadrature signal and hold the sampledpeak voltages to produce a voltage level control signal representing acurrent absolute magnitude of the amplitude of the power signal; anerror amplifier configured to receive the reference voltage, the voltagelevel control signal, and a damping signal, where the error amplifiercircuit is further configured to subtract the error signal and thedamping signal from the reference voltage in order to produce a dutycycle modulation signal; a duty cycle modulator circuit configured toreceive the duty cycle modulation signal and, responsive thereto,produce a field voltage control signal, where the field voltage controlsignal oscillates at a predetermined frequency with a duty cyclecontrolled by the duty cycle modulation signal; and a stabilizer circuitconfigured to receive the field voltage control signal and, responsivethereto, low-pass filter the field voltage control signal in order toproduce the damping signal.
 2. The automatic voltage regulator circuitof claim 1, where the voltage regulator circuit further includes a powercircuit configured to receive the field voltage control signal and,responsive thereto, produce a field current configured to drive a fieldwinding of a generator that produces the power signal.
 3. The automaticvoltage regulator circuit of claim 1, where: the automatic voltageregulator circuit further includes a frequency control circuitconfigured to receive a frequency reference voltage and the phase errorsignal and subtract the frequency reference voltage from the phase errorsignal to produce a frequency control signal representing a phasecorrection for the power signal; and the error amplifier circuit isfurther configured to receive the frequency control signal and subtractthe frequency control signal from the reference voltage in producing theduty cycle modulation signal.
 4. The automatic voltage regulator circuitof claim 1, where the error amplifier circuit is further configured toreceive a droop control signal and subtract the droop control signalfrom the reference voltage in producing the duty cycle modulationsignal.
 5. The automatic voltage regulator circuit of claim 1, where thefield voltage control signal produced by the duty cycle modulatorcircuit is a pulse width modulated signal.
 6. The automatic voltageregulator circuit of claim 1, where the phase locked loop of thequadrature signal generator circuit operates at a lock frequency that isat least four times the oscillation frequency of the power signal. 7.The automatic voltage regulator circuit of claim 1, where the sample andhold circuit is further configured to convert the quadrature signal to ashort duration switching pulse aligned with the peaks of the full waverectified power signal.
 8. The automatic voltage regulator circuit ofclaim 1, where: the automatic voltage regulator circuit further includesa digital frequency control circuit configured to: receive the phaseerror signal and convert it to a digital phase error signal; multiplythe digital phase error signal by a voltage to Hertz slope parameter,subtract a reference voltage parameter, and multiply by a scaling factorto produce a scaled frequency error signal; compare the scaled frequencyerror signal to a frequency threshold parameter and, if the scaledfrequency error signal value is less than the frequency thresholdparameter, set a frequency control value to a reference valuecorresponding to a desired frequency of the power signal, and,otherwise, set the frequency control value to the frequency thresholdparameter; multiply the frequency control value by an output voltagelevel parameter to produce a digital frequency control signal; andconvert the digital frequency control signal to an analog frequencycontrol signal; and the error amplifier circuit is further configured toreceive the analog frequency control signal and subtract the analogfrequency control signal from the reference voltage in producing theduty cycle modulation signal.
 9. The automatic voltage regulator circuitof claim 1, where the error amplifier comprises a digital erroramplifier circuit configured to: receive the voltage level controlsignal and convert it to a digital voltage level control signal; receiveand low pass filter the field voltage control signal to produce adamping signal; convert the damping signal to a digital damping signal;multiple the digital damping signal by a predetermined damping factor toproduce a modified digital damping signal; compute a difference betweenthe modified digital damping signal and the digital voltage levelcontrol signal to produce a digital difference signal; multiply thedigital difference signal by a predetermined gain factor to produce anamplified digital difference signal; and pulse width modulation encodethe amplified digital difference signal to produce the duty cyclemodulation signal.
 10. A method for automatic voltage regulation of agenerator, the method comprising the steps: full wave rectifying a powersignal of the generator; sampling the power signal and comparing thepower signal to a DC reference voltage signal that corresponds to adesired steady state operating voltage level for the power signal inorder to generate a line sync signal synchronized to an oscillationfrequency of the power signal; producing first and second phase signalsthat are synchronized to the line sync signal and 90° out of phase withone another; using a phase locked loop to lock onto the frequency of theline sync signal using a lock frequency that is at least twice theoscillation frequency of the power signal and generating a phase errorsignal that corresponds to a phase difference between the line syncsignal and an oscillating frequency of the phase locked loop; using thefirst and second phase signals to generate a quadrature signal that isin quadrature with the line sync signal; sampling the peak voltages ofthe full wave rectified power signal using the quadrature signal andholding the sampled peak voltages to produce a voltage level controlsignal representing a current absolute magnitude of the amplitude of thepower signal; subtracting the error signal and the damping signal fromthe reference voltage in order to produce a duty cycle modulationsignal; using the duty cycle modulation signal to produce a fieldvoltage control signal, where the field voltage control signaloscillates at a predetermined frequency with a duty cycle controlled bythe duty cycle modulation signal; and low-pass filtering the fieldvoltage control signal in order to produce the damping signal.
 11. Themethod for automatic voltage regulation of a generator of claim 10,where the method further includes using the field voltage control signalto produce a field current configured to drive a field winding of thegenerator.
 12. The method for automatic voltage regulation of agenerator of claim 10, where: the method further includes subtracting afrequency reference voltage from the phase error signal to produce afrequency control signal representing a phase correction for the powersignal; and the step of producing the duty cycle modulation signalfurther includes subtracting the frequency control signal from thereference voltage.
 13. The method for automatic voltage regulation of agenerator of claim 10, the method further including receiving a droopcontrol signal and subtracting the droop control signal from thereference voltage in producing the duty cycle modulation signal.
 14. Themethod for automatic voltage regulation of a generator of claim 10,where the field voltage control signal further comprises a pulse widthmodulated signal.
 15. The method for automatic voltage regulation of agenerator of claim 10, where the step of using a phase locked loop tolock onto the frequency of the line sync signal further comprisesoperating the phase locked loop at a lock frequency that is at leastfour times the oscillation frequency of the power signal.
 16. The methodfor automatic voltage regulation of a generator of claim 10, where thestep of sampling the peak voltages of the full wave rectified powersignal using the quadrature signal further includes converting thequadrature signal to a short duration switching pulse aligned with thepeaks of the full wave rectified power signal.
 17. The method forautomatic voltage regulation of a generator of claim 10, where themethod further includes the steps of: converting the phase error signalto a digital phase error signal; multiplying the digital phase errorsignal by a voltage to Hertz slope parameter, subtracting a referencevoltage parameter, and multiplying by a scaling factor to produce ascaled frequency error signal; comparing the scaled frequency errorsignal to a frequency threshold parameter and, if the scaled frequencyerror signal value is less than the frequency threshold parameter,setting a frequency control value to a reference value corresponding toa desired frequency of the power signal, and, otherwise, setting thefrequency control value to the frequency threshold parameter;multiplying the frequency control value by an output voltage levelparameter to produce a digital frequency control signal; and convertingthe digital frequency control signal to an analog frequency controlsignal; and the step of producing the duty cycle modulation signalfurther comprises receiving the analog frequency control signal andsubtracting the analog frequency control signal from the referencevoltage to produce the duty cycle modulation signal.
 18. The method forautomatic voltage regulation of a generator of claim 10, where themethod further includes the steps of: converting the voltage levelcontrol signal to a digital voltage level control signal; low passfiltering the field voltage control signal to produce a damping signal;converting the damping signal to a digital damping signal; multiplyingthe digital damping signal by a predetermined damping factor to producea modified digital damping signal; computing a difference between themodified digital damping signal and the digital voltage level controlsignal to produce a digital difference signal; multiplying the digitaldifference signal by a predetermined gain factor to produce an amplifieddigital difference signal; and pulse width modulation encoding theamplified digital difference signal to produce the duty cycle modulationsignal.
 19. An automatic voltage regulation system for a synchronousgenerator, the system comprising: means for full wave rectifying a powersignal of the generator; means for sampling the power signal andcomparing the power signal to a DC reference voltage signal thatcorresponds to a desired steady state operating voltage level for thepower signal in order to generate a line sync signal synchronized to anoscillation frequency of the power signal; means for producing first andsecond phase signals that are synchronized to the line sync signal and90° out of phase with one another; means for using a phase locked loopto lock onto the frequency of the line sync signal using a lockfrequency that is at least twice the oscillation frequency of the powersignal and generating a phase error signal that corresponds to a phasedifference between the line sync signal and an oscillating frequency ofthe phase locked loop; means for using the first and second phasesignals to generate a quadrature signal that is in quadrature with theline sync signal; means for sampling the peak voltages of the full waverectified power signal using the quadrature signal and holding thesampled peak voltages to produce a voltage level control signalrepresenting a current absolute magnitude of the amplitude of the powersignal; means for subtracting the error signal and the damping signalfrom the reference voltage in order to produce a duty cycle modulationsignal; means for using the duty cycle modulation signal to produce afield voltage control signal, where the field voltage control signaloscillates at a predetermined frequency with a duty cycle controlled bythe duty cycle modulation signal; and means for low-pass filtering thefield voltage control signal in order to produce the damping signal. 20.The automatic voltage regulation system of claim 19, where the systemfurther includes means for using the field voltage control signal toproduce a field current configured to drive a field winding of thegenerator.
 21. The automatic voltage regulation system of claim 19,where the system further includes: means for subtracting a frequencyreference voltage from the phase error signal to produce a frequencycontrol signal representing a phase correction for the power signal; andthe means for producing the duty cycle modulation signal furtherincludes means for subtracting the frequency control signal from thereference voltage.
 22. The automatic voltage regulation system of claim19, where the system further includes means for subtracting a droopcontrol signal from the reference voltage in producing the duty cyclemodulation signal.
 23. The automatic voltage regulation system of claim19, where the field voltage control signal further comprises a pulsewidth modulated signal.
 24. The automatic voltage regulation system ofclaim 19, where the means for using a phase locked loop to lock onto thefrequency of the line sync signal further comprises means for operatingthe phase locked loop at a lock frequency that is at least four timesthe oscillation frequency of the power signal.
 25. The automatic voltageregulation system of claim 19, where the means for sampling the peakvoltages of the full wave rectified power signal using the quadraturesignal further includes means for converting the quadrature signal to ashort duration switching pulse aligned with the peaks of the full waverectified power signal.